Hyperbolic equilibrium point: Difference between revisions

Revision as of 20:07, 12 November 2013

In electronics, diode modelling refers to the mathematical models used to approximate the actual behavior of real diodes to enable calculations and circuit analysis. A diode's I-V curve is nonlinear (it is well described by the Shockley diode law). This nonlinearity complicates calculations in circuits involving diodes so simpler models are often required.

This article discusses the modelling of p-n junction diodes, but the techniques may be generalized to other solid state diodes.

Large-signal modelling

Shockley diode model

The Shockley diode equation relates the diode current $I$ of a p-n junction diode to the diode voltage $V_{D}$ . This relationship is the diode I-V characteristic:

I = I_{S} (e^{V_{D} / (n V_{T})} - 1)

,

where $I_{S}$ is the saturation current or scale current of the diode (the magnitude of the current that flows for negative $V_{D}$ in excess of a few $V_{T}$ , typically 10⁻¹² A). The scale current is proportional to the cross-sectional area of the diode. Continuing with the symbols: $V_{T}$ is the thermal voltage ( $k T / q$ , about 26 mV at normal temperatures), and $n$ is known as the diode ideality factor (for silicon diodes $n$ is approximately 1 to 2).

When $V_{D} ≫ n V_{T}$ the formula can be simplified to:

I \approx I_{S} \cdot e^{V_{D} / (n V_{T})}

.

This expression is, however, only an approximation of a more complex I-V characteristic. Its applicability is particularly limited in case of ultrashallow junctions, for which better analytical models exist.^[1]

Diode-resistor circuit example

To illustrate the complications in using this law, consider the problem of finding the voltage across the diode in Figure 1.

Figure 1: Diode circuit with resistive load.

Because the current flowing through the diode is the same as the current throughout the entire circuit, we can lay down another equation. By Kirchhoff's laws, the current flowing in the circuit is

I = \frac{V_{S} - V_{D}}{R}

.

These two equations determine the diode current and the diode voltage. To solve these two equations, we could substitute the current $I$ from the second equation into the first equation, and then try to rearrange the resulting equation to get $V_{D}$ in terms of $V_{S}$ . A difficulty with this method is that the diode law is nonlinear. Nonetheless, a formula expressing $I$ directly in terms of $V_{S}$ without involving $V_{D}$ can be obtained using the Lambert $W$ -function, which is the inverse function of $f (w) = w e^{w}$ , that is, $w = W (f)$ . This solution is discussed next.

Explicit solution

An explicit expression for the diode current can be obtained in terms of the Lambert W-function (also called the Omega function). A guide to these manipulations follows. A new variable $w$ is introduced as

w = \frac{I_{S} R}{n V_{T}} (\frac{I}{I_{S}} + 1)

.

Following the substitutions $I / I_{S} = e^{V_{D} / n V_{T}} - 1$ :

w e^{w} = \frac{I_{S} R}{n V_{T}} e^{V_{D} / n V_{T}} e^{\frac{I_{S} R}{n V_{T}} (\frac{I}{I_{S}} + 1)}

and $V_{D} = V_{S} - I R$ :

w e^{w} = \frac{I_{S} R}{n V_{T}} e^{V_{S} / n V_{T}} e^{\frac{- I R}{n V_{T}}} e^{\frac{I R I_{S}}{n V_{T} I_{S}}} e^{I_{S} R / n V_{T}}

rearrangement of the diode law in terms of w becomes:

w e^{w} = \frac{I_{S} R}{n V_{T}} e^{(V_{s} + I_{s} R) / (n V_{T})}

,

which using the Lambert $W$ -function becomes

w = W (\frac{I_{S} R}{n V_{T}} e^{(V_{s} + I_{s} R) / (n V_{T})})

.

With the approximations (valid for the most common values of the parameters) $I_{s} R ≪ V_{S}$ and $I / I_{S} ≫ 1$ , this solution becomes

I \approx \frac{n V_{T}}{R} W (\frac{I_{S} R}{n V_{T}} e^{V_{s} / (n V_{T})})

.

Once the current is determined, the diode voltage can be found using either of the other equations.

For large x, $W (x)$ can be approximated by $W (x) = \ln x - \ln \ln x + o (1) .$ . For common physical parameters and resistances, $\frac{I_{S} R}{n V_{T}} e^{V_{s} / (n V_{T})}$ will be on the order of 10⁴⁰.

Iterative solution

The diode voltage $V_{D}$ can be found in terms of $V_{S}$ for any particular set of values by an iterative method using a calculator or computer ^[2] The diode law is rearranged by dividing by $I_{S}$ , and adding 1. The diode law becomes

\frac{I}{I_{S}} + 1 = e^{V_{D} / (n V_{T})}

.

By taking natural logarithms of both sides the exponential is removed, and the equation becomes

\frac{V_{D}}{n V_{T}} = \ln (\frac{I}{I_{S}} + 1)

.

For any $I$ , this equation determines $V_{D}$ . However, $I$ also must satisfy the Kirchhoff's law equation, given above. This expression is substituted for $I$ to obtain

\frac{V_{D}}{n V_{T}} = \ln (\frac{(V_{S} - V_{D}) / R}{I_{S}} + 1)

,

or

V_{D} = n V_{T} \ln (\frac{V_{S} - V_{D}}{R I_{S}} + 1)

.

The voltage of the source $V_{S}$ is a known given value, but $V_{D}$ is on both sides of the equation, which forces an iterative solution: a starting value for $V_{D}$ is guessed and put into the right side of the equation. Carrying out the various operations on the right side, we come up with a new value for $V_{D}$ . This new value now is substituted on the right side, and so forth. If this iteration converges the values of $V_{D}$ become closer and closer together as the process continues, and we can stop iteration when the accuracy is sufficient. Once $V_{D}$ is found, $I$ can be found from the Kirchhoff's law equation.

Sometimes an iterative procedure depends critically on the first guess. In this example, almost any first guess will do, say $V_{D} = 600 m V$ . Sometimes an iterative procedure does not converge at all: in this problem an iteration based on the exponential function does not converge, and that is why the equations were rearranged to use a logarithm. Finding a convergent iterative formulation is an art, and every problem is different.

Graphical solution

Graphical analysis is a simple way to derive a numerical solution to the transcendental equations describing the diode. As with most graphical methods, it has the advantage of easy visualization. By plotting the I-V curves, it is possible to obtain an approximate solution to any arbitrary degree of accuracy. This process is the graphical equivalent of the two previous approaches, which are more amenable to computer implementation.

This method plots the two current-voltage equations on a graph and the point of intersection of the two curves satisfies both equations, giving the value of the current flowing through the circuit and the voltage across the diode. The following figure illustrates such method.

Piecewise linear model

In practice, the graphical method is complicated and impractical for complex circuits. Another method of modelling a diode is called piecewise linear (PWL) modelling. In mathematics, this means taking a function and breaking it down into several linear segments. This method is used to approximate the diode characteristic curve as a series of linear segments. The real diode is modelled as 3 components in series: an ideal diode, a voltage source and a resistor. The figure below shows a real diode I-V curve being approximated by a two-segment piecewise linear model. Typically the sloped line segment would be chosen tangent to the diode curve at the Q-point. Then the slope of this line is given by the reciprocal of the small-signal resistance of the diode at the Q-point.

Mathematically idealized diode

Firstly, let us consider a mathematically idealized diode. In such an ideal diode, if the diode is reverse biased, the current flowing through it is zero. This ideal diode starts conducting at 0 V and for any positive voltage an infinite current flows and the diode acts like a short circuit. The I-V characteristics of an ideal diode are shown below:

Ideal diode in series with voltage source

Now let us consider the case when we add a voltage source in series with the diode in the form shown below:

Ideal diode with a series voltage source.

When forward biased, the ideal diode is simply a short circuit and when reverse biased, an open circuit. If the anode of the diode is connected to 0 V, the voltage at the cathode will be at Vt and so the potential at the cathode will be greater than the potential at the anode and the diode will be reverse biased. In order to get the diode to conduct, the voltage at the anode will need to be taken to Vt. This circuit approximates the cut-in voltage present in real diodes. The combined I-V characteristic of this circuit is shown below:

The Shockley diode model can be used to predict the approximate value of $V_{t}$ .

I = I_{S} (e^{V_{D} / (n \cdot V_{T})} - 1) \Leftrightarrow

\ln (1 + \frac{I}{I_{S}}) = \frac{V_{D}}{n \cdot V_{T}} \Leftrightarrow

V_{D} = n \cdot V_{T} \ln (1 + \frac{I}{I_{S}}) \approx n \cdot V_{T} \ln (\frac{I}{I_{S}}) \Leftrightarrow

V_{D} \approx n \cdot V_{T} \cdot \ln 10 \cdot \log_{10} (\frac{I}{I_{S}})

Using $n = 1$ and $T = 25 C$ :

V_{D} \approx 0.05916 \cdot \log_{10} (\frac{I}{I_{S}})

Typical values of the saturation current at room temperature are:

$I_{S} = 1 0^{- 12}$ for silicon diodes;
$I_{S} = 1 0^{- 6}$ for germanium diodes.

As the variation of $V_{D}$ goes with the logarithm of the ratio $\frac{I}{I_{S}}$ , its value varies very little for a big variation of the ratio. The use of base 10 logarithms makes it easier to think in orders of magnitude.

For a current of 1.0 mA:

$V_{D} \approx 0.53 V$ for silicon diodes (9 orders of magnitude);
$V_{D} \approx 0.18 V$ for germanium diodes (3 orders of magnitude).

For a current of 100 mA:

$V_{D} \approx 0.65 V$ for silicon diodes (11 orders of magnitude);
$V_{D} \approx 0.30 V$ for germanium diodes (5 orders of magnitude).

Values of 0.6 or 0.7 Volts are commonly used for silicon diodes ^[3]

Diode with voltage source and current-limiting resistor

The last thing needed is a resistor to limit the current, as shown below:

The I-V characteristic of the final circuit looks like this:

File:Diode Modelling Image11.png

I-V characteristic of an ideal diode with a series voltage source and resistor.

The real diode now can be replaced with the combined ideal diode, voltage source and resistor and the circuit then is modelled using just linear elements. If the sloped-line segment is tangent to the real diode curve at the Q-point, this approximate circuit has the same small-signal circuit at the Q-point as the real diode.

Dual PWL-diodes or 3-Line PWL model

File:PWL diode characteristic.PNG

I-V characteristic of the standard PWL model (marked by red-triangles), as described above. Shown for reference is the standard Shockley-diode model (marked by blue-diamonds). The Shockley parameters are Is=1e-12A, Vt=0.0258v

When more accuracy is desired in modelling the diode's turn-on characteristic, the model can be enhanced by doubling-up the standard PWL-model. This model uses two piecewise-linear diodes in parallel, as a way to model a single diode more accurately.

File:Diode 2piece linear model.png

PWL Diode model with 2 branches. The top branch has a lower forward-voltage and a higher resistance. This allows the diode to switch on more gradually, and in this regard more accurately models a real diode. The bottom branch has a higher forward voltage and a lower resistance, thus allowing high current at high voltage

File:Piecewise diode vs shockley1.PNG

Plot of the I-V Characteristic of this model (marked by red-triangles), as compared to the standard Shockley-diode model (marked by blue-diamonds). The Shockley parameters are Is=1e-12A, Vt=0.0258v

Small-signal modelling

Resistance

Using the Shockley equation, the small-signal diode resistance $r_{D}$ of the diode can be derived about some operating point (Q-point) where the DC bias current is $I_{Q}$ and the Q-point applied voltage is $V_{Q}$ .^[4] To begin, the diode small-signal conductance $g_{D}$ is found, that is, the change in current in the diode caused by a small change in voltage across the diode, divided by this voltage change, namely:

g_{D} = \frac{d I}{d V} |_{Q} = \frac{I_{0}}{V_{T}} e^{V_{Q} / V_{T}} \approx \frac{I_{Q}}{V_{T}}

.

The latter approximation assumes that the bias current $I_{Q}$ is large enough so that the factor of 1 in the parentheses of the Shockley diode equation can be ignored. This approximation is accurate even at rather small voltages, because the thermal voltage $V_{T} \approx 25 m V$ at 300K, so $V_{Q} / V_{T}$ tends to be large, meaning that the exponential is very large.

Noting that the small-signal resistance $r_{D}$ is the reciprocal of the small-signal conductance just found, the diode resistance is independent of the ac current, but depends on the dc current, and is given as

r_{D} = \frac{n \cdot V_{T}}{I_{Q}}

.

Capacitance

The charge in the diode carrying current $I_{Q}$ is known to be

Q = I_{Q} τ_{F} + Q_{J}

,

where $τ_{F}$ is the forward transit time of charge carriers:^[4] The first term in the charge is the charge in transit across the diode when the current $I_{Q}$ flows. The second term is the charge stored in the junction itself when it is viewed as a simple capacitor; that is, as a pair of electrodes with opposite charges on them. It is the charge stored on the diode by virtue of simply having a voltage across it, regardless of any current it conducts.

In a similar fashion as before, the diode capacitance is the change in diode charge with diode voltage:

C_{D} = \frac{d Q}{d V_{Q}} = \frac{d I_{Q}}{d V_{Q}} τ_{F} + \frac{d Q_{J}}{d V_{Q}} \approx \frac{I_{Q}}{V_{T}} τ_{F} + C_{J}

,

where $C_{J} = \begin{matrix} \frac{d Q_{J}}{d V_{Q}} \end{matrix}$ is the junction capacitance and the first term is called the diffusion capacitance, because it is related to the current diffusing through the junction.

Variation of Forward Voltage with Temperature

The above equation has an exponential of $V_{D} / (k T / q)$ , which would lead one to expect that the forward-voltage increases with temperature. In fact, this is generally not the case: As temperature rises, the saturation current $I_{S}$ rises, and this effect dominates. So as the diode becomes hotter, the forward-voltage (for a given current) decreases.

Here is some detailed experimental experimental data, which shows this for a 1N4005 silicon diode. In fact, some silicon diodes are used as temperature sensors, for example the CY7 series (datasheet) has a forward voltage of 1.02V in liquid nitrogen (77K), 0.54V at room temperature, and 0.29V at 100 degC.

In addition there is a small change of the material parameter bandgap with temperature. For LEDs, this bandgap change also changes their colour: they move towards the blue end of the spectrum when cooled.

Since the diode forward-voltage drops as its temperature rises, this can lead to Thermal_runaway, especially in bipolar-transistor circuits, where a change in bias leads to an increase in power-dissipation, which in turn changes the bias even further.

References

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[1]

[2]

[3]

[4]

Hyperbolic equilibrium point: Difference between revisions

en>Flyer22

Revision as of 20:07, 12 November 2013

Contents

Large-signal modelling

Shockley diode model

Diode-resistor circuit example

Explicit solution

Iterative solution

Graphical solution

Piecewise linear model

Mathematically idealized diode

Ideal diode in series with voltage source

Diode with voltage source and current-limiting resistor

Dual PWL-diodes or 3-Line PWL model

Small-signal modelling

Resistance

Capacitance

Variation of Forward Voltage with Temperature

References

See also

Navigation menu

@@ Line 1: / Line 1: @@
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+In [[electronics]], '''diode modelling''' refers to the mathematical models used to approximate the actual behavior of real diodes to enable calculations and circuit analysis. A [[diode]]'s [[Electrical current|I]]-[[Voltage|V]] curve is [[nonlinear]] (it is well described by the [[Diode#Shockley diode equation|Shockley diode law]]). This nonlinearity complicates calculations in circuits involving diodes
+so simpler models are often required.
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+This article discusses the modelling of [[p-n junction]] diodes, but the techniques may be generalized to other [[Solid state (electronics)|solid state]] diodes.
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-== Ray Ban Wayfarer opzionale ==
+==Large-signal modelling==
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+===Shockley diode model===
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+The [[Diode#Shockley diode equation|Shockley diode equation]] relates the diode current  <math>I</math>  of a [[p-n junction]] diode to the diode voltage <math>V_D</math>. This relationship is the diode ''I-V characteristic'':
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-== Pandora Bracciali  probabilmente ==
+::<math>I=I_S\left(e^{V_D/(nV_T)}-1\right)</math>,
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+where <math>I_S</math> is the ''saturation current'' or ''scale current'' of the diode (the magnitude of the current that flows for negative <math>V_D</math> in excess of a few <math>V_T</math>, typically 10<sup>−12</sup> A). The scale current is proportional to the cross-sectional area of the diode. Continuing with the symbols:  <math>V_ T</math> is the [[thermal voltage]] (<math>kT/q</math>, about 26&nbsp;mV at normal temperatures), and <math>n</math> is known as the diode ideality factor (for silicon diodes <math>n</math> is approximately 1 to 2).
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-== La sua prima raccolta di poesie Borse Michael Kors ==
+When <math>V_D\gg nV_ T</math> the formula can be simplified to:
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+::<math>I \approx I_S \cdot e^{V_D/(nV_T)}</math>.
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-== tra cui il miliardario di moda gay Longchamp Milano ==
+This expression is, however, only an approximation of a more complex I-V characteristic. Its applicability is particularly limited in case of ultrashallow junctions, for which better analytical models exist.<ref name=Popadic>.
+{{cite journal
+|doi=10.1109/TED.2008.2009028
+|last1=Popadic
+|first1=Miloš
+|last2=Lorito
+|first2=Gianpaolo
+|last3=Nanver
+|first3=Lis K.
+|title=Analytical Model of I – V Characteristics of Arbitrarily Shallow p-n Junctions
+|year= 2009
+|pages=116–125
+|volume=56
+|journal=IEEE Transactions on Electron Devices
+|url=http://ieeexplore.ieee.org/search/srchabstract.jsp?arnumber=4717238&isnumber=4723893&punumber=16&k2dockey=4717238@ieeejrns&query=%28+%28%28electron+devices%29%3Cin%3Emetadata+%29+%3Cand%3E+%28%28popadic%29%3Cin%3Emetadata+%29+%29&pos=0&access=no
+}}
+</ref>
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+====Diode-resistor circuit example====
+To illustrate the complications in using this law, consider the problem of finding the voltage across the diode in Figure 1.
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+[[File:Diode Modelling Image2.svg|frame|Figure 1: Diode circuit with resistive load.]]
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+Because the current flowing through the diode is the same as the current throughout the entire circuit, we can lay down another equation. By [[Kirchhoff's circuit laws|Kirchhoff's laws]], the current flowing in the circuit is
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-== . Bracciale Tiffany ==
+::<math>I= \frac{V_S-V_D}{R}  </math>.
+These two equations determine the diode current and the diode voltage. To solve these two equations, we could substitute the current <math>I</math> from the second equation into the first equation, and then try to rearrange the resulting equation to get <math>V_D</math> in terms of <math>V_S</math>. A difficulty with this method is that the diode law is nonlinear. Nonetheless, a formula expressing <math>I</math> directly in terms of <math>V_S</math> without involving <math>V_D</math> can be obtained using the ''Lambert <math>W</math>-function'', which is the [[inverse function]] of <math>f(w) = we^w</math>, that is, <math>w = W(f)</math>. This solution is discussed next.
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+=====Explicit solution=====
+An explicit expression for the diode current can be obtained in terms of the [[Lambert W function|Lambert ''W''-function]] (also called the Omega function). A guide to these manipulations follows. A new variable <math>w</math> is introduced as
-   <li>[http://yijiansong.u092.iiddcc.com/news/html/?343109.html http://yijiansong.u092.iiddcc.com/news/html/?343109.html]</li>
-   <li>[http://www.philatelie-france-russie.fr/spip.php?article51/ http://www.philatelie-france-russie.fr/spip.php?article51/]</li>
-   <li>[http://www.milonga.ru/news/detail/1444.html?ref=mnogoru http://www.milonga.ru/news/detail/1444.html?ref=mnogoru]</li>
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- </ul>
-== pipistrelli Occhiali Da Sole Ray Ban ==
+::<math> w = \frac{I_SR}{nV_T} \left(\frac {I}{I_S}+1\right ) </math>.
-'I genitori diventano molto appassionato e arrabbiato quando i loro figli non possono portare il burro di arachidi a scuola', ha dichiarato Mike Tringale, direttore degli affari esterni al Asthma and Allergy Foundation of America. E non ha rivelato che la sponsorizzazione. <br><br>Piante, come molti tipi di zecche o trifoglio, interessi e sull'uso di api, pipistrelli, uccelli, ecc per la rimozione del polline da un fiore all'altro. Tuttavia, i prestiti del patrimonio netto non viene fatto a livello personale in modo da capire come l'equità può essere utilizzato per finanziare un business è qualcosa che tutti i nuovi arrivati dovrebbero capire.. <br><br>Certo, i Cougars non otterrebbe il cachet conferenza potere, ma almeno avrebbe giocato un programma nazionale e sono stati abbastanza rilevanti per colpire la propria offerta TV con ESPN. Ci sono stati grandi investimenti di capitale in uranio, [http://www.mutuisi.it/area_riservata/gestione_news/editor.asp Occhiali Da Sole Ray Ban] nickel, oro, rame, potassa, e l'esplorazione diamante. <br><br>Dense nubi di polvere turbinano intorno Zaatari, la città [http://www.metallipressofusi.it/web_ted/include/datebase.asp Pandora Anelli] improvvisata di 140.000 rifugiati siriani che sono fuggiti nel deserto giordano. Anche se la cannabis rimane illegale a livello federale, l'amministrazione Obama ha segnalato che permetterà legalizzazione di procedere in Colorado e Washington Stato, che ha approvato una legge simile.. <br><br>Twitter ha appena 200 milioni di conti rispetto a Facebook miliardi plus. Dopo tutto, in attesa per ore per l'idraulico per arrivare il tuo soggiorno è inondata da una grande perdita non può essere un'esperienza molto piacevole. Io sono un ragazzo che è in camion e può solo sognare di guidare attraverso i 50 stati più bassi. <br><br>Quindi, che la sua festa si celebra il 13 dicembre è significativo. In conclusione, i dati presentati devono fornire prove più che sufficienti per suggerire che il mercato immobiliare residenziale in Australia (in particolare sbarcare mercato) è enormemente sopravvalutato, guidato dal debito finanziato la speculazione e la non [http://www.comandulli.it/includi/about.asp Nike Blazer] tassazione relativa della rendita fondiaria. <br><br>Ho cambiato. Questa migrazione ha coltivato la crescita del mercato immobiliare in Jharkhand.. Magneto concorda con Storm e ritiene che questa cura non è altro che il tentativo del governo a un tipo di purificazione razziale di tutti i mutanti. È quindi possibile taggare dove hai trovato questa specie tramite GPS, in modo che altri leafsnappers potete vedere, in [http://www.comandulli.it/includi/about.asp Nike Blazer Basse] modo da costruire un database di flora locali in tutto il mondo. <br><br>L'intenzione della proposta di legge è quello di costringere i datori di lavoro per coprire più dipendenti da assicurazione sanitaria; tuttavia i critici del disegno di legge affermazione che l'imposta di sanità dipendente proposta porterà solo a più disoccupazione..<ul>
+Following the substitutions <math>I/I_S=e^{V_D/nV_T}-1</math>:
-   <li>[http://www.proyectoalba.com.ar/spip.php?article66/&quot;/ http://www.proyectoalba.com.ar/spip.php?article66/&quot;/]</li>
+::<math> w e^w = \frac{I_SR}{nV_T} e^{V_D/nV_T} e^{\frac{I_SR}{nV_T} \left(\frac {I}{I_S}+1 \right )} </math>
-   <li>[http://www.163sy.com/home.php?mod=spacecp&ac=blog&blogid= http://www.163sy.com/home.php?mod=spacecp&ac=blog&blogid=]</li>
+and <math>V_D = V_S-IR</math>:
-   <li>[http://bbs.nuanf.cn/forum.php?mod=viewthread&tid=136776 http://bbs.nuanf.cn/forum.php?mod=viewthread&tid=136776]</li>
+::<math> w e^w = \frac{I_SR}{nV_T} e^{V_S/nV_T} e^{\frac{-IR}{nV_T}} e^{\frac{IR I_S}{nV_T I_S}} e^{I_SR/nV_T} </math>
-   <li>[http://1.ts.cn/home.php?mod=space&uid=2635&do=blog&quickforward=1&id=6102081 http://1.ts.cn/home.php?mod=space&uid=2635&do=blog&quickforward=1&id=6102081]</li>
+rearrangement of the diode law in terms of ''w'' becomes:
-   <li>[http://202.109.115.218:8080/read.php?tid=9329698 http://202.109.115.218:8080/read.php?tid=9329698]</li>
+::<math>w e^w =\frac{I_SR}{nV_T} e^{(V_s+I_sR)/(nV_T)} </math>,
- </ul>
+which using the Lambert <math>W</math>-function becomes
+::<math>w = W\left( \frac{I_SR}{nV_T} e^{(V_s+I_sR)/(nV_T)}\right) </math>.
+With the approximations (valid for the most common values of the parameters) <math>I_sR \ll V_S</math> and <math>I/I_S \gg 1</math>, this solution becomes
+::<math>I \approx \frac{n V_T}{R} W \left(\frac{I_S R}{n V_T} e^{V_s/(n V_T)}\right)</math>.
+Once the current is determined, the diode voltage can be found using either of the other equations.
+For large x, <math>W(x)</math> can be approximated by <math>W(x)=\ln x-\ln\ln x+o(1).</math>. For common physical parameters and resistances, <math>\frac{I_S R}{n V_T} e^{V_s/(n V_T)}</math> will be on the order of 10<sup>40</sup>.
+=====Iterative solution=====
+The diode voltage <math>V_D</math> can be found in terms of <math>V_S</math> for any particular set of values by an [[iterative method]] using a calculator or computer <ref name=Sedra2>.
+{{cite book
+|author=A.S. Sedra and K.C. Smith
+|title=Microelectronic Circuits
+|year= 2004
+|edition=Fifth
+|publisher=Oxford
+|location=New York
+|isbn=0-19-514251-9
+|pages=Example 3.4 p. 154
+|url=http://worldcat.org/isbn/0195142519
+|nopp=true}}
+</ref> The diode law is rearranged by dividing by <math>I_S</math>, and adding 1. The diode law becomes
+::<math>\frac {I}{I_S}+1=e^{V_D/(nV_T)}</math>.
+By taking natural logarithms of both sides the exponential is removed, and the equation becomes
+::<math>\frac{V_D}{nV_T} = \ln \left(\frac {I}{I_S}+1\right)  </math>.
+For any <math>I</math>, this equation determines <math>V_D</math>. However, <math>I</math> also must satisfy the Kirchhoff's law equation, given above. This expression is substituted for <math>I</math> to obtain
+::<math>\frac{V_D}{nV_T} = \ln \left(\frac {(V_S-V_D)/R}{I_S}+1\right)  </math>,
+or
+::<math>V_D = nV_T \ln \left(\frac {V_S-V_D}{R I_S}+1\right)  </math>.
+The voltage of the source <math>V_S</math> is a known given value, but <math>V_D</math> is on both sides of the equation, which forces an iterative solution: a starting value for <math>V_D</math> is guessed and put into the right side of the equation. Carrying out the various operations on the right side, we come up with a new value for <math>V_D</math>. This new value now is substituted on the right side, and so forth. If this iteration ''converges'' the values of <math>V_D</math> become closer and closer together as the process continues, and we can stop iteration when the accuracy is sufficient. Once <math>V_D</math> is found, <math>I</math> can be found from the Kirchhoff's law equation.
+Sometimes an iterative procedure depends critically on the first guess. In this example, almost any first guess will do, say <math>V_D = 600\,\mathrm{mV}</math>. Sometimes an iterative procedure does not converge at all: in this problem an iteration based on the exponential function does not converge, and that is why the equations were rearranged to use a logarithm. Finding a convergent iterative formulation is an art, and every problem is different.
+===== Graphical solution =====
+Graphical analysis is a simple way to derive a numerical solution to the [[transcendental function|transcendental]] equations describing the diode. As with most graphical methods, it has the advantage of easy visualization. By plotting the ''I''-''V'' curves, it is possible to obtain an approximate solution to any arbitrary degree of accuracy.  This process is the graphical equivalent of the two previous approaches, which are more amenable to computer implementation.
+This method plots the two current-voltage equations on a graph and the point of intersection of the two curves satisfies both equations, giving the value of the current flowing through the circuit and the voltage across the diode. The following figure illustrates such method.
+[[File:Diode Modelling Image3.jpg|thumb|center|300px|Graphical determination of the operating point through the intersection of the diode characteristic with the resistive load line.]]
+===Piecewise linear model===
+In practice, the graphical method is complicated and impractical for complex circuits. Another method of modelling a diode is called '''[[piecewise linear function|piecewise linear]]''' (PWL) '''modelling'''. In mathematics, this means taking a function and breaking it down into several linear segments. This method is used to approximate the diode characteristic curve as a series of linear segments. The real diode is modelled as 3 components in series: an ideal diode, a voltage source and a [[resistor]]. The figure below shows a real diode I-V curve being approximated by a two-segment piecewise linear model. Typically the sloped line segment would be chosen tangent to the diode curve at the [[Q-point]]. Then the slope of this line is given by the reciprocal of the [[small-signal]] resistance of the diode at the Q-point.
+[[File:Diode Modelling Image10.jpg|thumb|center|300px|A piecewise linear approximation of the diode characteristic.]]
+==== Mathematically idealized diode ====
+Firstly, let us consider a mathematically idealized diode. In such an ideal diode, if the diode is reverse biased, the current flowing through it is zero. This ideal diode starts conducting at 0 V and for any positive voltage an infinite current flows and the diode acts like a short circuit. The I-V characteristics of an ideal diode are shown below:
+[[File:Diode Modelling Image5.png|thumb|center|300px|I-V characteristic of an ideal diode.]]
+==== Ideal diode in series with voltage source ====
+Now let us consider the case when we add a voltage source in series with the diode in the form shown below:
+[[File:Diode Modelling Image6.jpg|thumb|right|300px|Ideal diode with a series voltage source.]]
+When forward biased, the ideal diode is simply a short circuit and when reverse biased, an open circuit.
+If the [[anode]] of the diode is connected to 0 V, the voltage at the [[cathode]] will be at ''Vt'' and so the potential at the cathode will be greater than the potential at the anode and the diode will be reverse biased. In order to get the diode to conduct, the voltage at the anode will need to be taken to ''Vt''. This circuit approximates the cut-in voltage present in real diodes. The combined I-V characteristic of this circuit is shown below:
+[[File:Diode Modelling Image8.png|thumb|center|300px|I-V characteristic of an ideal diode with a series voltage source.]]
+The Shockley diode model can be used to predict the approximate value of <math>V_t</math>.
+::<math>I = I_S \left( e^{V_D/(n \cdot V_T)}-1 \right) \Leftrightarrow</math>
+::<math>\ln \left( 1 + \frac{I}{I_S} \right) = \frac{V_D}{n \cdot V_T} \Leftrightarrow</math>
+::<math>V_D = n \cdot V_T \ln\left(1+\frac{I}{I_S}\right) \approx n \cdot V_T \ln \left( \frac{I}{I_S} \right)  \Leftrightarrow</math>
+::<math>V_D \approx n \cdot V_T \cdot \ln{10} \cdot \log_{10}{\left( \frac{I}{I_S} \right)}
+</math>
+Using <math>n = 1</math> and <math>T = 25 C</math>:
+::<math>V_D \approx 0.05916 \cdot \log_{10}{\left( \frac{I}{I_S} \right)}</math>
+Typical values of the [[saturation current]] at room temperature are:
+*<math>I_S = 10^{-12} </math> for silicon diodes;
+*<math>I_S = 10^{-6} </math> for germanium diodes.
+As the variation of <math>V_D</math> goes with the logarithm of the ratio <math>\frac{I}{I_S}</math>, its value varies very little for a big variation of the ratio. The use of base 10 logarithms makes it easier to
+think in orders of magnitude.
+For a current of 1.0 mA:
+*<math>V_D \approx 0.53 V</math> for silicon diodes (9 orders of magnitude);
+*<math>V_D \approx 0.18 V</math> for germanium diodes (3 orders of magnitude).
+For a current of 100 mA:
+*<math>V_D \approx 0.65 V</math> for silicon diodes (11 orders of magnitude);
+*<math>V_D \approx 0.30 V</math> for germanium diodes (5 orders of magnitude).
+Values of 0.6 or 0.7 Volts are commonly used for silicon diodes <ref name=Kal>.
+{{cite book
+  | last = Kal
+  | first = Santiram
+  | title = Basic Electronics: Devices, Circuits and IT Fundamentals
+  | chapter = Chapter 2
+  | year = 2004
+  | publisher = Prentice-Hall of India Pvt.Ltd
+   | isbn = 81-203-1952-4
+  | edition = Section 2.5: Circuit Model of a P-N Junction Diode }}</ref>
+====Diode with voltage source and current-limiting resistor====
+The last thing needed is a resistor to limit the current, as shown below:
+[[File:Diode Modelling Image9.jpg|thumb|right|300px|Ideal diode with a series voltage source and resistor.]]
+The ''I-V'' characteristic of the final circuit looks like this:
+[[File:Diode Modelling Image11.png|thumb|center|300px|I-V characteristic of an ideal diode with a series voltage source and resistor.]]
+The real diode now can be replaced with the combined ideal diode, voltage source and resistor and the circuit then is modelled using just linear elements. If the sloped-line segment is tangent to the real diode curve at the [[Q-point]], this approximate circuit has the same [[small-signal]] circuit at the Q-point as the real diode.
+==== Dual PWL-diodes or 3-Line PWL model ====
+[[File:PWL diode characteristic.PNG|thumb|left|450px|I-V characteristic of the standard PWL model (marked by red-triangles), as described above. Shown for reference is the standard Shockley-diode model (marked by blue-diamonds). The Shockley parameters are Is=1e-12A, Vt=0.0258v]]
+When more accuracy is desired in modelling the diode's turn-on characteristic, the model can be enhanced by doubling-up the standard PWL-model.  This model uses two piecewise-linear diodes in parallel, as a way to model a single diode more accurately.
+[[File:Diode 2piece linear model.png|thumb|right|400px|PWL Diode model with 2 branches. The top branch has a lower forward-voltage and a higher resistance. This allows the diode to switch on more gradually, and in this regard more accurately models a real diode. The bottom branch has a higher forward voltage and a lower resistance, thus allowing high current at high voltage]]
+[[File:Piecewise diode vs shockley1.PNG|thumb|left|450px|Plot of the I-V Characteristic of this model (marked by red-triangles), as compared to the standard Shockley-diode model (marked by blue-diamonds). The Shockley parameters are Is=1e-12A, Vt=0.0258v]]
+<br clear="all" />
+==Small-signal modelling==
+===Resistance===
+Using the Shockley equation, the small-signal diode resistance <math>r_D</math> of the diode can be derived about some operating point ([[Q-point]]) where the DC bias current is <math>I_Q</math> and the Q-point applied voltage is <math>V_Q</math>.<ref name=jaeger/> To begin, the diode ''small-signal conductance'' <math>g_D</math> is found, that is, the change in current in the diode caused by a small change in voltage across the diode, divided by this voltage change, namely:
+::<math> g_D=\frac{dI}{dV}\Big|_Q = \frac{I_0}{V_T} e^{V_Q/V_T}  \approx \frac{I_Q}{V_T} </math>.
+The latter approximation assumes that the bias current <math>I_Q</math> is large enough so that the factor of 1 in the parentheses of the Shockley diode equation can be ignored.  This approximation is accurate even at rather small voltages, because the [[thermal voltage]] <math>V_T \approx 25\,\mathrm{mV}</math> at 300K, so <math>V_Q/V_T</math> tends to be large, meaning that the exponential is very large.
+Noting that the small-signal resistance <math>r_D</math> is the reciprocal of the small-signal conductance just found, the diode resistance is independent of the ac current, but depends on the dc current, and is given as
+::<math>r_D=\frac {n \cdot V_T}{I_Q}</math>.
+===Capacitance===
+The charge in the diode carrying current <math>I_Q</math> is known to be
+:<math>Q=I_Q\tau_F +Q_J</math>,
+where <math>\tau_F</math> is the forward transit time of charge carriers:<ref name=jaeger>{{cite book | title = Microelectronic Circuit Design | edition= second | author = R.C. Jaeger and T.N. Blalock | publisher = McGraw-Hill | year = 2004 | isbn = 0-07-232099-0 | url = http://books.google.com/?id=u6vH4Gsrlf0C&pg=PA883&dq=%22Microelectronic+Circuit+Design%22+inauthor:Jaeger+small-signal+diode }}</ref> The first term in the charge is the charge in transit across the diode when the current <math>I_Q</math> flows. The second term is the charge stored in the junction itself when it is viewed as a simple [[capacitance|capacitor]]; that is, as a pair of electrodes with opposite charges on them. It is the charge stored on the diode by virtue of simply having a voltage across it, regardless of any current it conducts.
+In a similar fashion as before, the diode capacitance is the change in diode charge with diode voltage:
+::<math> C_D = \frac{dQ}{dV_Q} =\frac{dI_Q}{dV_Q} \tau_F + \frac {dQ_J}{dV_Q} \approx \frac {I_Q}{V_T} \tau_F+ C_J </math>,
+where <math> C_J = \begin{matrix}\frac {dQ_J}{dV_Q}\end{matrix}</math> is the junction capacitance and the first term is called the [[diffusion capacitance]], because it is related to the current diffusing through the junction.
+== Variation of Forward Voltage with Temperature ==
+The above equation has an exponential of  <math>V_D/(kT/q)</math>, which would lead one to expect that the forward-voltage increases with temperature. In fact, this is generally not the case: As temperature rises, the saturation current <math>I_S </math> rises, and this effect dominates. So as the diode becomes ''hotter'', the forward-voltage (for a given current) ''decreases''.
+Here is some detailed experimental [http://www.cliftonlaboratories.com/1n400x_diode_family_forward_voltage.htm#Forward_Drop_versus_Temperature_and_Current experimental data], which shows this for a 1N4005 silicon diode. In fact, some silicon diodes are used as temperature sensors, for example the CY7 series ([http://www.omega.com/Temperature/pdf/CY7.pdf datasheet]) has a forward voltage of 1.02V in liquid nitrogen (77K), 0.54V at room temperature, and 0.29V at 100 degC.
+In addition there is a small change of the material parameter bandgap with temperature.
+For LEDs, this bandgap change also changes their colour: they move towards the blue end of the spectrum when cooled.
+Since the diode forward-voltage drops as its temperature rises,  this can lead to [[Thermal_runaway]], especially in bipolar-transistor circuits, where a change in bias leads to an increase in power-dissipation, which in turn changes the bias even further.
+==References==
+{{reflist}}
+==See also==
+* [[Bipolar junction transistor]]
+* [[Semiconductor device modeling|Semiconductor device modelling]]
+[[Category:Electronic device modeling]]

Hyperbolic equilibrium point: Difference between revisions

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Revision as of 20:07, 12 November 2013

Large-signal modelling

Shockley diode model

Diode-resistor circuit example

Explicit solution

Iterative solution

Graphical solution

Piecewise linear model

Mathematically idealized diode

Ideal diode in series with voltage source

Diode with voltage source and current-limiting resistor

Dual PWL-diodes or 3-Line PWL model

Small-signal modelling

Resistance

Capacitance

Variation of Forward Voltage with Temperature

References

See also

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